# Intercarrier Interference (ICI) with OFDM signals

What is the relationship between Intercarrier Interference (ICI) in OFDM signals and Doppler spread? Is there a mathematical property to determine what OFDM parameters, such as subcarrier spacing, should be selected to overcome X hertz of Doppler spread such that ICI is avoided?

• complicated question! Let's work up from 0 to solution: Do you understand how Doppler leads to ICI in OFDM receivers? Mar 25, 2022 at 10:13
• nope, let's not make this already very broad question broader than it is. If you need an explanation, please do say so! But that would probably mean you should ask "how does Doppler shift lead to ICI in OFDM". But you say you have an idea, so where does the question whether CP length and subcarrier spacing come into play? I mean, if you have the general idea, then one of these parameters matters. Would be super helpful if you could explain how you come to ask about these two specifically! Mar 25, 2022 at 12:37
• @MarcusMüller was that an invitation Marcus or were you going to jump in and have some math and illustrating fun? Mar 26, 2022 at 2:16
• @MarcusMüller Ok wow, I see that is exactly the question for this answer. I should copy my answer there- I believe what AlexTP is showing is the predicted ISI within any one OFDM symbol, which should predict the rotation I depict which also should ultimately simplify to the delay in time / linear phase in frequency relationship in the DFT. What I did which was different so subject to scrutiny is use a power combining model since over the course of many symbols we are dealing with random data and no longer need to be concerned with coherent phase combining of those individual ICI errors. Agree? Mar 27, 2022 at 12:12
• exactly; very rarely would someone care about the exact sum of the ICI in each subcarrier over many symbols – any reasonable bit-level interleaving would hopefully make ICI uncorrelated to the individual symbol being interfered, so that a sum-of-variances consideration is valid! Mar 27, 2022 at 12:22

As Marcus mentioned in the comments under the original question, this is complicated with lots to understand. Thankfully, the framework is already here with other posts to at least pursue Marcus' suggestion: start with understanding the simpler case of a fixed frequency offset (due to Doppler from a fixed velocity between transmitter and receiver as well as the inevitable frequency offset between independent transmitter and receiver clocks). The result of this will both be easier to show and best introduce the relationship between frequency offset and Intercarrier Interference (ICI) with OFDM modulation. I close with the further details to consider when going from "ICI" to "Doppler Spread".

Doppler Spread is not avoided, but equalized in the receiver assuming a sufficiently long cyclic prefix to capture the related delay spread, and that the resulting fading is reduced to flat fading due to the relatively long OFDM symbols so that a "single tap equalizer" is essentially used on each bin in the receiver. So to answer this post specifically, the key requirement is the length of the CP exceeds the expected delay spread, and the bandwidth of each subcarrier is less than the coherence bandwidth of the channel.

I detail the relationship between ICI and frequency offset below, but if this isn't at all clear, please proceed to the bottom with related links, references and background information that should further help this all make sense.

Bottom Line

The general case for the total ICI power relative to a subcarrier versus carrier offset in units of subcarrier spacing $$k$$:

$$n(k) = \sum_n^{N-1} \bigg(\frac{\sin(\pi (n-k))}{N \sin(\pi (n-k)/N)}\bigg)^2$$

With the signal power component reduced according to:

$$s(k)= \bigg(\frac{\sin(\pi k)}{N \sin(\pi k/N)}\bigg)^2$$

From this the SNR due to the ICI from a normalized frequency offset $$k$$ would be given as:

$$SNR(k) = 10 log_{10}(s(k)/n(k))$$

and Error Vector Magnitude (EVM) given as $$EVM = -SNR$$ assuming the EVM is computed as being normalized by total constellation power (see this post).

Where:

$$N$$ is the total number of subcarriers

$$k$$ is the frequency offset normalized to the subcarrier spacing

This is the expected SNR due to the effects of ICI alone at a frequency offset $$k$$, where $$k$$ is the normalized frequency in units of the subcarrier spacing. (For example if we had a subcarrier spacing of 78.125 KHz, and a frequency offset of 100 Hz, $$k = 100/78125 = 1.28E-3$$).

ICI vs Frequency Offset for OFDM

A simple frequency offset is referred to as Carrier Frequency Offset (CFO) and would create a static rotation for all the subcarriers in one OFDM symbol (the constellation for every subcarrier would be rotated by the same phase relative to the previous OFDM symbol), and from one symbol to the next, each the constellations will rotate in time at the rate of the frequency offset.

So if we for example if we introduced a CFO of 1 Hz, and watched the constellation for any one subcarrier over several RB's we would observe it rotating at 1 cycle/second (in addition to the modulation itself changing its magnitude and phase).

(Interesting time frequency duality is to note that this is uniquely different from a time offset, in which case each of the subcarriers within an OFDM symbol would rotate relative to each other, but each would remain at the same phase from symbol to symbol -- both properties are used to resolve and correct for such offsets).

The graphic below is illustrating the concept of rotation in the sub-carrier constellation. In this case the constellation shown is for a QPSK modulation, such that every 2 bits of data are mapped to one of four possible states and used to set the magnitude and phase for a particular sub-carrier as a bin in the DFT. As described above this rotation can be due to either CFO or time delay offset as distinguished by us observing the rotation in time (from one OFDM symbol to the next) for the case of CFO, or in frequency (from one subcarrier to the next within a single OFDM symbol) for the case of time delay offset. So over each observation the constellation is rotating from one of the red locations, to one of the green locations, to one of the four locations.

To understand how this then results in ICI, we will use the magnitude response of each bin in the DFT. We note as further detailed in the references below that each bin of the DFT has a magnitude frequency response given by the Dirichlet Kernel (approaching a Sinc function as the number of DFT bins gets large, and can be described as an "aliased Sinc function"). The Dirichlet Kernel has a magnitude that is given as:

$$|D(\omega)| = \frac{\sin(N\omega/2)}{N \sin(\omega/2)}$$

Where:

$$\omega$$ is the normalized radian frequency in units of radians/sample with $$2\pi$$ corresponding to the subcarrier spacing times the total number of bins: $$\omega \in [0, 2\pi)$$ for $$N \in [0, N)$$

$$N$$ is the total number of bins in the DFT (total number of subcarriers).

To express this in units of subcarriers (DFT bins), as a frequency index $$k$$, the expression would be:

$$k = \frac{\omega N}{2\pi}$$

$$|D(k)| = \frac{\sin(\pi k)}{N \sin(\pi k/N)}$$

The mechanism for ICI is clear after considering a simple case of a small DFT with 4 bins. The magnitude of the frequency response for all 4 bins in plotted below, as given by the Dirichlet Kernel centered on each bin (note these colors have no association with the colors used above):

Note what we are seeing in the plot above with regards to OFDM: This represents 4 sub-carriers, and the magnitude of the frequency response we would see for each subcarrier using rectangular pulse shaped modulation. Under conditions of modulation with random data, the square of this would be the expected power spectral density for each sub-carrier. When we have perfect synchronization between transmitter and receiver with no Doppler, and no time offsets, then the modulation is aligned such that the frequency index above represents the bin center of each DFT computed in the receiver. We see above that bin 0 would only be responding to the modulation in the "blue" carrier, and bin 1 would only be responding to the modulation in the "orange" carrier, etc... as the response of every other carrier at that particular frequency index is 0.

Any small shift in the frequency index, as depicted below, would lead to energy in subcarriers leaking into the demodulation of other sub-carriers, which is specifically ICI.

From this and the formula for the underlying Dirichlet Kernel, we can compute the resulting total ICI as an SNR or EVM degradation. Given the independence of each of the leakage terms from each sub-carrier, the leakage from each will accumulate as a root-sum-square (will add in power). For example, for the case above if we assumed the offset frequency was the equivalent of 0.1 bins, we can compute the total the SNR degradation for the first bin as follows (each term is squared to be a power term, which we can then sum and convert the result to dB using $$10Log()$$:

$$N=4$$. The signal component which is specifically at $$k=0.1$$ with reference to the blue trace will reduce according to:

$$P_{sig} = |D(k)|^2|_{k=0.1} = \bigg(\frac{\sin(\pi 0.1)}{4 \sin(\pi 0.1/4)}\bigg)^2 \approx 0.969$$

The biggest ICI will come from the adjacent subcarrier as given by the orange trace which has an offset from our signal of $$k=0.9$$:

$$P_{n1} = |D(k)|^2|_{k=0.9} = \bigg(\frac{\sin(\pi .9)}{4 \sin(\pi .9/4)}\bigg)^2 \approx 0.014$$

And similarly the remaining two subcarriers (the green trace and red trace) would each contribute:

$$P_{n2} = |D(k)|^2|_{k=1.9} \approx 0.006$$

$$P_{n3} = |D(k)|^2|_{k=2.9} \approx 0.010$$

The the total SNR in dB for this case would be:

$$SNR = 10log_{10} = \frac{P_{sig}}{P_{n1}+P_{n2}+P_{n3}} = 15.0 \text{ dB}$$

And the EVM would be $$-SNR = -15.0$$ dB (or in per-cent $$10^{-15/20}= 17.8 \text{%}$$.

From this we see the general case for the total ICI power relative to a subcarrier versus carrier offset in units of subcarrier spacing $$k$$:

$$n(k) = \sum_n^{N-1} \bigg(\frac{\sin(\pi (n-k))}{N \sin(\pi (n-k)/N)}\bigg)^2$$

With the signal component reduced according to:

$$s(k)= \bigg(\frac{\sin(\pi k)}{N \sin(\pi k/N)}\bigg)^2$$

As further detailed below, this is specifically the simpler case with a fixed frequency offset, while Doppler Spread involves a "spread" in frequency of many such offsets.

Related Background Details

The following links and details are important to completely understand this answer:

The basics of the DFT (and that the FFT is just an algorithm to solve the DFT: this post can help.

A basic understanding of OFDM and the relationship between the subcarriers and the DFT operations that are used: this post can help.

The terminology of an "OFDM Symbol" is the desired block of user data encoded in a fixed length DFT, with each DFT bin representing a modulation constellation (typically given by QPSK or QAM modulation), such that each bin in the DFT has a magnitude and phase corresponding to the constellation mapped for that symbol duration.

With the FFT sufficiently understood, and how it is used for OFDM as a way to send MANY relatively low bandwidth QPSK/QAM modulations in parallel basically, the next item to really understand is spectral leakage and the "filter bank" view of the DFT. For that I recommend reading this post.

Once the relationship of ICI from a single frequency offset is understood from the answer given in this post, understand that the typical channel consists of a spread of multiple frequency offsets due to the time varying fading due to motion of the transmitter, receiver, or objects causing reflections- so a single tone demonstration does not really provide a true representation of what "Doppler Spread" is all about; it only gives us the insight into the relationship between a simple frequency offset and ICI. Multiple reflections cause the same signal to arrive at different times, resulting in delay spread as further detailed here. When those time delays (causing phase variations) are time varying, we will also see a similar spreading in the frequency, which is referred to as Doppler spread. This makes intuitive sense when we understand that instantaneous frequency is the time derivative of phase, and for that consider phase as a rotation rather than a delay- a changing rotation angle with time such as a bicycle wheel results in the frequency of rotation and is related by a derivative or rate of change).

Related to the fact that there is delay spread is the need and use of the "Cyclic Prefix" (CP). The relationship of frequency offset with ICI can be completely understood without getting into the details of the CP, but I encourage the understanding of this related detail as well as a fundamental feature of OFDM. This post may help, as well as many other posts here which can be found by searching for "Cyclic Prefix", but an important foundational understanding is periodicity in the DFT: The non-zero results of a DFT of a selection of a waveform over time $$T$$ will be identical to the DFT over $$NT$$ for any integer $$N$$. This leads to circular convolution properties all which will help makes sense of the need for the CP for operation in fading channels with delay spread.

• Thanks for the detailed and helpful answer! Mar 27, 2022 at 11:39
• wow yeah, I didn't realize how seriously you'd take the invitation:) Mar 27, 2022 at 12:01
• @MarcusMüller it was a "where do you start" question, and you gave the right direction. Mar 27, 2022 at 12:06
• @MarcusMüller Very appreciated if you could you also confirm my second paragraph just added...? I didn't have my second cup of coffee yet. Mar 27, 2022 at 12:41